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mp2364 dual 1.5a, 23v, 1.4mhz step-down converter mp2364 rev. 1.6 www.monolithicpower.com 1 1/22/2010 mps proprietary information. unaut horized photocopy and duplication prohibited. ? 2010 mps. all rights reserved. the future of analog ic technology description the mp2364 is a dual monolithic step-down switch mode converter with built-in internal power mosfets. it achieves 1.5a continuous output current for each output over a wide input supply range with excellent load and line regulation. current mode operation provides fast transient response and eases loop stabilization. fault condition protection includes cycle-by-cycle current limiting and thermal shutdown. in shutdown mode, the regulator draws 40a of supply current. the mp2364 requires a minimum number of readily available standard external components. evaluation board reference board number dimensions ev2364df-01a 2.2?x x 1.6?y x 0.4?z features ? 1.5a current for each output ? 0.18 ? internal power mosfet switches ? stable with low esr output ceramic capacitors ? up to 90% efficiency ? 40a shutdown mode ? fixed 1.4mhz frequency ? thermal shutdown ? cycle-by-cycle over current protection ? wide 4.75v to 23v operating input range ? each output adjustable from 0.92v to 16v ? configurable for single output with double the current ? programmable under voltage lockout ? programmable soft-start ? available in a tssop20 with an exposed pad. applications ? distributed power systems ? i/o and core supplies ? dsl modems ? set top boxes ? cable modems ?mps? and ?the future of analog ic technology? are registered trademarks of monolithic power systems, inc. typical application mp2364 ssb bsb nc2 inb swb pgb sgb fba compa ena 10 9 8 7 6 5 4 3 2 1 ssa nc1 bsa ina swa pga sga fbb compb enb 20 19 18 17 16 15 14 13 12 11 7.5k ? 3.3nf 5uh 5uh 22uf 25.5k ? 10nf 0.47uf 10uf 10uf 10k ? 82pf 10nf 22uf 0.47uf 16.9k ? 10k ? 2.5v @ 1.5a off on off on 2a schottky 2a schottky 12v 3.3v @ 1.5a 10k ? 2.2nf v in =12v l=5 h 100 90 80 70 60 50 efficiency (%) 0 0.5 1.0 1.5 load current (a) efficiency vs load current v out =5v v out =3.3v v out =2.5v
mp2364 ? dual 1.5a, 23v, 1.4mhz step-down converter mp2364 rev. 1.6 www.monolithicpower.com 2 1/22/2010 mps proprietary information. unaut horized photocopy and duplication prohibited. ? 2010 mps. all rights reserved. package reference part number* package temperature mp2364df tssop20f ?40 c to +85 c * for tape & reel, add suffix ?z (eg. mp2364df?z) for lead free, add suffix ?lf (eg. mp2364df?lf?z) absolute maxi mum ratings (1) supply voltage ( ina, inb )................................ 25v switch voltage ( swa, swb ).............................. 26v bootstrap voltage ( bsa, bsb ) .................. v sw + 6v feedback voltage ( fba, fbb ) ............ ?0.3v to +6v enable/uvlo voltage ( ena, enb ) ..... ?0.3v to +6v comp voltage ( compa, compb ) .......... ?0.3v to +6v soft start voltage ( ssa, ssb )............. ?0.3v to +6v junction temperature.............................+150 c lead temperature ..................................+260 c storage temperature ..............?65c to +150 c recommended operating conditions (2) supply voltage (v in ) ...................... 4.75v to 23v operating temperature.................?40 c to +85 c thermal resistance (3) ja jc tssop20f ............................. 40 ....... 6.... c/w notes: 1) exceeding these ratings may damage the device. 2) the device is not guaranteed to function outside of its operating conditions. 3) measured on approximately 1? square of 1 oz copper. ssa nc1 bsa ina swa pga sga fbb compb enb 1 2 3 4 5 6 7 8 9 10 20 19 18 17 16 15 14 13 12 11 ena compa fba sgb pgb swb inb nc2 bsb ssb top view exposed pad for tssop20f only
mp2364 ? dual 1.5a, 23v, 1.4mhz step-down converter mp2364 rev. 1.6 www.monolithicpower.com 3 1/22/2010 mps proprietary information. unaut horized photocopy and duplication prohibited. ? 2010 mps. all rights reserved. electrical characteristics v in = 12v, t a = +25 c, unless otherwise noted. parameter symbol condition min typ max units feedback voltage v fb 4.75v v in 23v 0.892 0.920 0.948 v upper switch-on resistance r ds(on)1 0.18 ? lower switch-on resistance r ds(on)2 10 ? upper switch leakage v en = 0v, v sw = 0v 10 a current limit (4) 2.5 3.0 a current limit gain output current to comp pin voltage g cs 1.95 a/v error amplifier voltage gain a vea 400 v/v error amplifier transconductance g ea ? i c = 10 a 630 930 1230 a/v oscillator frequency f osc 1.4 mhz short circuit frequency f sc v fb = 0v 210 khz soft-start pin equivalent output resistance 9 k ? en shutdown threshold voltage v en i cc > 100a 0.7 1.0 1.3 v enable pull-up current i en 1.0 a en uvlo threshold rising v uvlo v en rising 2.37 2.50 2.62 v en uvlo threshold hysteresis 210 mv supply current (shutdown) i off v en 0.4v 40 70 a supply current (quiescent) i on v en 3v 2.4 2.8 ma thermal shutdown d max 160 c maximum duty cycle v fb = 0.8v 70 % minimum on time t on 100 ns note: 4) equivalent output current = 1.5a 50% duty cycle 2.0a 50% duty cycle assumes ripple current = 30% of load current. slope compensation changes current limit above 40% duty cycle.
mp2364 ? dual 1.5a, 23v, 1.4mhz step-down converter mp2364 rev. 1.6 www.monolithicpower.com 4 1/22/2010 mps proprietary information. unaut horized photocopy and duplication prohibited. ? 2010 mps. all rights reserved. pin functions pin # name description 1 ssa soft-start control for channel a. 9k ? output resistance from the pin. set rc time constant with external capacitor for soft start ramp time. ramp time = 2.2 x 9k ? x c. 2 nc no connect 3 bsa high-side driver boost pin. connect a 10nf capacitor from this pin to swa. 4 ina supply voltage channel a. the mp2364 operates from a +4.75v to +23v unregulated input. input ceramic capacitors should be close to this pin. 5 swa switch channel a. this connects the inductor to either ina through m1a or to pga through m2a. 6 pga power ground channel a. this is the power ground connection to the input capacitor ground. 7 sga signal ground channel a. this pin is the sign al ground reference for the regulated output voltage. for this reason care must be taken in its layout. this node should be placed outside of the d1 to c1 ground path to prevent swit ching current spikes from inducing voltage noise into the part. 8 fbb feedback voltage for channel b. this pin is the f eedback voltage. the output voltage is ratio scaled through a voltage divider, and the center point of t he divider is connected to this pin. the voltage is compared to the on board 0.92v reference. 9 compb compensation channel b. this is the output of the transconductance error amplifier. a series rc is placed on this pin for proper control loop compensation. please refer to more in the datasheet. 10 enb enable/uvlo channel b. a voltage greater than 2.62v enables operation. leave enb unconnected for automatic startup. an under voltage lockout (uvlo) function can be implemented by the addition of a resistor divider from v in to gnd. for complete low current shutdown the enb pin voltage needs to be less than 700mv. 11 ssb soft-start control for channel b. 9k ? output resistance from the pin. set rc time constant with external capacitor for soft st art ramp time. ramp time = 2.2x9k ? xc. 12 bsb high-side driver boost pin. connect a 10nf capacitor from this pin to swb. 13 nc no connect. 14 inb supply voltage channel b. the mp2364 operates from a +4.75v to +23v unregulated input. input ceramic capacitors should be close to this pin. 15 swb switch channel b. this connects the inductor to either inb through m1b or to pgb through m2b. 16 pgb power ground channel b. this is the power ground connection to the input capacitor ground. 17 sgb signal ground channel b. this pin is the sign al ground reference for the regulated output voltage. for this reason care must be taken in its layout. this node should be placed outside of the d1 to c1 ground path to prevent swit ching current spikes from inducing voltage noise into the part. 18 fba feedback voltage for channel a. this pin is the f eedback voltage. the output voltage is ratio scaled through a voltage divider, and the center point of t he divider is connected to this pin. the voltage is compared to the on board 0.92v reference. 19 compa compensation channel a. this is the output of the transconductance error amplifier. a series rc is placed on this pin for proper control loop compensation. please refer to more in the datasheet. 20 ena enable/uvlo channel a. a voltage greater than 2.62v enables operation. leave ena unconnected for automatic startup. an under voltage lockout (uvlo) function can be implemented by the addition of a resistor divider from v in to gnd. for complete low current shutdown the ena pin voltage needs to be less than 700mv.
mp2364 ? dual 1.5a, 23v, 1.4mhz step-down converter mp2364 rev. 1.6 www.monolithicpower.com 5 1/22/2010 mps proprietary information. unaut horized photocopy and duplication prohibited. ? 2010 mps. all rights reserved. operation the mp2364 is a dual channel current mode regulator. the comp pin voltage is proportional to the peak inductor current. at the beginning of a cycle, the upper transistor m1 is off, and the lower transistor m2 is on (see figure 1). the comp pin voltage is higher than the current sense amplifier output, and the current comparator?s output is low. the rising edge of the 1.4mhz clk signal sets the rs flip-flop. its output turns off m2 and turns on m1 thus connecting the sw pin and inductor to the input supply. the increasing inductor current is sensed and amplified by the current sense amplifier. ramp compensation is summed to current sense amplifier output and compared to the error amplifier output by the current comparator. when the sum of the current sense amplifier output and the slope compensation signal exceeds the comp pin voltage, the rs flip- flop is reset. the mp2364 reverts to its initial m1 off, m2 on state. if the sum of the current sense amplifier output and the slope compensation signal does not exceed the comp voltage, the falling edge of the clk resets the flip-flop. the output of the error amplifier integrates the voltage difference between the feedback and the 0.92v bandgap reference. the polarity is such that a voltage at the fb pin lower than 0.92v increases the comp pin voltage. since the comp pin voltage is proportional to the peak inductor current, an increase in its voltage increases current delivered to the output. the lower 10 ? switch ensures that the bootstrap capacitor voltage is charged during light load conditions. external schottky diode d1 carries the inductor current when m1 is off (see figure 1). lockout comparator error amplifier frequency foldback comparator gm = 930ua/v internal regulators 1 a 1.8v 9k ? slope comp clk current comparator current sense amplifier shutdown comparator ssa/ ssb oscillator 210/1400khz s r q m1 0.18 ? m2 10 ? 5v + q 0.7v + + 2.29v/ 2.50v + 0.4v + + -- -- -- -- -- -- 0.92v compa/ compb fba / fbb sga/ sgb pga/ pgb swa/ swb bsa/ bsb ena/ enb ina/ inb figure 1?functional block diagram (diagram portrays ? of the mp2364)
mp2364 ? dual 1.5a, 23v, 1.4mhz step-down converter mp2364 rev. 1.6 www.monolithicpower.com 6 1/22/2010 mps proprietary information. unaut horized photocopy and duplication prohibited. ? 2010 mps. all rights reserved. application information component selection the mp2364 has two channels: a and b. the following formulas are used for component selection of both channels. refer to components with reference ?a? for channel a, and components with reference ?b? for channel b, respectively, as indicated in figure 3 (i.e. ? r1a for channel a and r1b for channel b). setting the output voltage the output voltage is set using a resistive voltage divider from the output voltage to fb pin. the voltage divider divides the output voltage down to the feedback voltage by the ratio: 2 r 1 r 2 r v v out fb + = thus the output voltage is: 2 r 2 r 1 r v 92 . 0 v out + = where v fb is the feedback voltage and v out is the output voltage a typical value for r2 can be as high as 100k ? , but a typical value is 10k ? . using that value, r1 is determined by: ) 1 v 92 . 0 v ( 2 r 1 r out ? = for example, for a 3.3v output voltage, r2 is 10k ? , and r1 is 25.9k ? . inductor the inductor is required to supply constant current to the output load while being driven by the switched input voltage. a larger value inductor will result in less ripple current that will result in lower output ripple voltage. however, the larger value inductor will have a larger physical size, higher series resistance, and/or lower saturation current. a good rule for determining the inductance to use is to allow the peak-to-peak ripple current in the inductor to be approximately 30% of the maximum switch current limit. also, make sure that the peak inductor current is below the maximum switch current limit. the inductance value can be calculated by: ? ? ? ? ? ? ? ? ? = in out l s out v v 1 ? i f v 1 l where v in is the input voltage, f s is the switching frequency, and ? i l is the peak-to- peak inductor ripple current. choose an inductor that will not saturate under the maximum inductor peak current. the peak inductor current can be calculated by: ? ? ? ? ? ? ? ? ? + = in out s out load lp v v 1 1 l f 2 v i i where i load is the load current. output rectifier diode the output rectifier diode supplies the current to the inductor when the high-side switch is off. to reduce losses due to the diode forward voltage and recovery times, use a schottky diode. choose a diode whose maximum reverse voltage rating is greater than the maximum input voltage, and whose current rating is greater than the maximum load current. input capacitor the input current to the step-down converter is discontinuous, therefore a capacitor is required to supply the ac current to the step-down converter while maintaining the dc input voltage. use low esr capacitors for the best performance. ceramic capacitors are preferred, but tantalum or low-esr electrolytic capacitors may also suffice. since the input capacitor (c1) absorbs the input switching current it requires an adequate ripple current rating. the rms current in the input capacitor can be estimated by: ? ? ? ? ? ? ? ? ? = in out in out load 1 c v v 1 v v i i the worst-case condition occurs at v in = 2v out , where: 2 i i load 1 c =
mp2364 ? dual 1.5a, 23v, 1.4mhz step-down converter mp2364 rev. 1.6 www.monolithicpower.com 7 1/22/2010 mps proprietary information. unaut horized photocopy and duplication prohibited. ? 2010 mps. all rights reserved. for simplification, choose the input capacitor whose rms current rating greater than half of the maximum load current. the input capacitor can be electrolytic, tantalum or ceramic. when using electrolytic or tantalum capacitors, a small, high quality ceramic capacitor, i.e. 0.1f, should be placed as close to the ic as possible. when using ceramic capacitors, make sure that they have enough capacitance to provide sufficient charge prevent excessive voltage ripple at input. the input voltage ripple caused by capacitance can be estimated by: ? ? ? ? ? ? ? ? ? = ? in out in out load in v v 1 v v 1 c i v output capacitor the output capacitor is required to maintain the dc output voltage. ceramic, tantalum, or low esr electrolytic capacitors are recommended. low esr capacitors are preferred to keep the output voltage ripple low. the output voltage ripple can be estimated by: ? ? ? ? ? ? ? ? + ? ? ? ? ? ? ? ? ? = ? 2 c f 8 1 r v v 1 1 l f v v s esr in out s out out where l1 is the inductor value, c2 is the output capacitance value, and r esr is the equivalent series resistance (esr) value of the output capacitor. in the case of ceramic capacitors, the impedance at the switching frequency is dominated by the capacitance. the output voltage ripple is mainly caused by the capacitance. for simplification, the output voltage ripple can be estimated by: ? ? ? ? ? ? ? ? ? = in out 2 s out out v v 1 2 c 1 l f 8 v ? v in the case of tantalum or electrolytic capacitors, the esr dominates the impedance at the switching frequency. for simplification, the output ripple can be approximated to: esr in out s out out r v v 1 1 l f v ? v ? ? ? ? ? ? ? = the characteristics of the output capacitor also affect the stability of the regulation system. the mp2364 can be optimized for a wide range of capacitance and esr values. compensation components the mp2364 employs current mode control on each channel for easy compensation and fast transient response. the system stability and transient response are controlled through the comp pin. comp pin is the output of the internal transconductance error amplifier. a series capacitor-resistor combination sets a pole-zero combination to control the characteristics of the control system. the dc gain of the voltage feedback loop is given by: out fb vea cs load vdc v v a g r a = where a vea is the error amplifier voltage gain, g cs is the current sense transconductance and r load is the load resistor value. the system has two poles of importance. one is due to the compensation capacitor (c3) and the output resistor of error amplifier, and the other is due to the output capacitor and the load resistor. these poles are located at: vea ea 1 p a 3 c 2 g f = load 2 p r 2 c 2 1 f = where g ea is the error amplifier transconductance. the system has one zero of importance, due to the compensation capacitor (c3) and the compensation resistor (r3). this zero is located at: 3 r 3 c 2 1 f 1 z = the system may have another zero of importance, if the output capacitor has a large capacitance and/or a high esr value. the zero, due to the esr and capacitance of the output capacitor, is located at: esr esr r 2 c 2 1 f =
mp2364 ? dual 1.5a, 23v, 1.4mhz step-down converter mp2364 rev. 1.6 www.monolithicpower.com 8 1/22/2010 mps proprietary information. unaut horized photocopy and duplication prohibited. ? 2010 mps. all rights reserved. in this case (as shown in figure 2), a third pole set by the compensation capacitor (c6) and the compensation resistor (r3) is used to compensate the effect of the esr zero on the loop gain. this pole is located at: 3 r 6 c 2 1 f 3 p = the goal of compensation design is to shape the converter transfer function to get a desired loop gain. the system crossover frequency where the feedback loop has the unity gain is important. lower crossover frequencies result in slower line and load transient responses, while higher crossover frequencies could cause system unstable. a good rule of thumb is to set the crossover frequency to below one-tenth of the switching frequency. to optimize the compensation components for conditions not listed in table 2, the following procedure can be used: 1. choose the compensation resistor (r3) to set the desired crossover frequency. determine the r3 value by the following equation: fb out cs ea c v v g g f 2 c 2 3 r = where f c is the desired crossover frequency, which is typically less than one tenth of the switching frequency. 2. choose the compensation capacitor (c3) to achieve the desired phase margin. for applications with typical inductor values, setting the compensation zero, f z1 , to below one forth of the crossover frequency provides sufficient phase margin. determine the c3 value by the following equation: c f 3 r 2 4 3 c > where r3 is the compensation resistor value. 3. determine if the second compensation capacitor (c6) is required. it is required if the esr zero of the output capacitor is located at less than half of the switching frequency, or the following relationship is valid: 2 f r 2 c 2 1 s esr < if this is the case, then add the second compensation capacitor (c6) to set the pole f p3 at the location of the esr zero. determine the c6 value by the equation: 3 r r 2 c 6 c esr = soft-start each channel is soft-start controlled with the ssa and ssb pins. use capacitors to control the ramp time using the equation: 4 c k 9 2 . 2 ramptime ? = external bootstrap diode an external bootstrap diode may enhance the efficiency of the regulator, the applicable conditions of external bst diode are: z v out =5v or 3.3v; and z duty cycle is high: d= in out v v >65% in these cases, an external bst diode is recommended from the output of the voltage regulator to bst pin, as shown in figure2 mp2364 sw bst c l bst c 5v or 3.3v out external bst diode in4148 + figure 2?add optional external bootstrap diode to enhance efficiency the recommended external bst diode is in4148, and the bst cap is 0.1~1 f.
mp2364 ? dual 1.5a, 23v, 1.4mhz step-down converter mp2364 rev. 1.6 www.monolithicpower.com 9 1/22/2010 mps proprietary information. unaut horized photocopy and duplication prohibited. ? 2010 mps. all rights reserved. pcb layout guide pcb layout is very important to achieve stable operation. please follow these guidelines and take figure3 for references. 1) keep the path of switching current short and minimize the loop area formed by input cap, high-side mosfet and schottky diode. 2) keep the connection of schottky diode between sw pin and input power ground as short and wide as possible. 3) ensure all feedback connections are short and direct. place the feedback resistors and compensation components as close to the chip as possible. 4) route sw away from sensitive analog areas such as fb. 5) connect in, sw, and especially gnd respectively to a large copper area to cool the chip to improve thermal performance and long-term reliability. l1a 1 2 3 4 5 6 7 8 9 10 20 19 18 17 16 15 14 13 12 11 ssa nc1 bsa ina swa pga sga fbb compb enb ena compa fba sgb pgb swb inb nc2 bsb ssb pgnd pgnd l1a d1b c2b r1a c1b d1a c2a c1a r2a c4a r4a c5a r3a c3a c6a c4b r4b r1b r2b r3b c3b c6b c5b top layer sgnd bottom layer figure3 D pcb layout
mp2364 ? dual 1.5a, 23v, 1.4mhz step-down converter mp2364 rev. 1.6 www.monolithicpower.com 10 1/22/2010 mps proprietary information. unaut horized photocopy and duplication prohibited. ? 2010 mps. all rights reserved. typical application circuits mp2364 ssb bsb nc2 inb swb pgb sgb fba compa ena 10 9 8 7 6 5 4 3 2 1 ssa nc1 bsa ina swa pga sga fbb compb enb 20 19 18 17 16 15 14 13 12 11 r3b 7.5k ? d1a b230a c3b 3.3nf l1a 5 h sumida cdrh6d28 l1b 5 h sumida cdrh6d28 c2a 22 f 6.3v r1a 25.5k ? 1% c5a 10nf c4a 0.47 f c1a 10 f 25v tdk ceramic c1b 10 f 25v tdk ceramic d1b b230a c5b 10nf c2b 22 f 6.3v c4b 0.47 f r1b 16.9k ? 1% r2b 10k ? 1% 2.5v @ 1.5a off on 3.3v @ 1.5a 12v r2a 10k ? off on c6a 82pf r3a 10k ? c3a 2.2nf figure 4?2.5v @ 1.5a and 3.3v @ 1.5a application circuit
mp2364 ? dual 1.5a, 23v, 1.4mhz step-down converter notice: the information in this document is subject to change wi thout notice. please contact m ps for current specifications. users should warrant and guarantee that third party intellectual property rights ar e not infringed upon when integrating mps products into any application. mps will not assume any legal responsibility for any said applications. mp2364 rev. 1.6 www.monolithicpower.com 11 1/22/2010 mps proprietary information. unaut horized photocopy and duplication prohibited. ? 2010 mps. all rights reserved. package information tssop20f note: 1) control dimension is in inches. dimension in bracket is millimeters. see detail "a" see detail "b" 0.004(0.090) 0.008(0.200) 0.007(0.190) 0.010(0.250) 0.004(0.090) 0.006(0.160) 0.075(0.190) 0.012(0.300) detail "b" 0.047(1.200) max 0.007(0.190) 0.012(0.300) 0.032(0.800) 0.041(1.050) 0.002(0.050) 0.006(0.150) 0.252 (6.400) 0.260 (6.600) seating plane 0.039(1.000)ref 0.010(0.250) 0.018(0.450) 0.030(0.750) 0 o -8 o detail "a" gate plane 0.004(0.090) 0.004(0.090) 0.0256(0.650)typ pin 1 ident. 0.169 0.177 (4.300) (4.500) 0.244 0.260 (6.200) (6.600) 0.030(0.750) 0.030(0.750) 0.105 (2.67) 0.118 (3.00) pad width 0.150 (3.80) 0.165 (4.19) pad length

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